Control of impedance of semiconductor amplifier circuits



H. L. BARNEY CONTROL OF IMPEDANCE 0F' SEMICGNDUCTOR AMPLIFIER CIRCUITS Feb. 13, 1951 Original Filed Nov. 6, 1948 Feb. 13, 1951 H. L. BARNl-:Y 2,541,322

CONTROL 0F IMPEDANCE 0F SEMICONDUCTOR AMPLIFIER CIRCUITS Original Filed Nov. 6, 1948 6 Sheets-Sheet 2 rnA/vs/s ron 60u/ VAL ENT 2000 CIRCUIT PARAMETERS OHMS [OOO

le (n4/LL MMM/Ms) INI/EN TOR BV H. L @ARA/Ey ATTO/@MEV H. L. BARNEY Feb. 13, 1951 CONTROL OF IMPEDANCE OF' SEMICONDUCTOR AMPLIFIER CIRCUITS 6 Sheets-Sheet 3 Original Filed Nov. 6, 1948 zo +e z/z (u I @I w a. m .b Z T w F U 0 vr RE W mm m mmv/m WL e H H. L. BARNEY Feb. 13, 1951 CONTROL OF IMPEDANCE OF' SEMICONDUCTOR AMPLIFIER CIRCUITS 6 Sheets-Sheet 4 Original Filed Nov. 6, 1948 UNSMELE REG/0N /NVE/VTOR HLaAR/vfr NWC/UMT- A TTORNEV Feb. 13, 1951 H. BARNEY 2,541,322

CONTROL OF IMPEDANCE 0F SEMICONDUCTOR AMPLIFIER CIRCUITS Original Filed Nov. 6, 1948 6 Sheets-Sheet 5 Haag H630 A TTORNE V Feb. 13,' 1951 H. L. BARNEY 2,541,322

y CONTROL OF' IMPEDANCE OF SEMICONDUCTOR AMPLIFIER CIRCUITS Original Filed Nov. 6,V 1948 6 Sheets-Sheet 6 ATTO/QMS y Patented Feb. 13, 1951 CONTROL OF IMPEDANCE OF SEMICON- y DUCTOR AMPLIFIER CIRCUITS Harold L. Barney, Madison, N. J., assigner to Bell Telephone Laboratories, Incorporated, New York, N. Y., a corporation of New York Original application November 6, 1948, Serial No. 58,684. Divided and this application November 15, 1949, Serial No. 127,440

1s cls-img. l

'I'his application is a division of application Serial No. 58,684, filed November 6, 1948.

This invention relates to signal translation networks utilizing semiconductor ampliers as active elements.

The principal object of the invention is to adjust the impedance of such a network, viewed at its input terminals or its output terminals, to a desired value.

More particular objects are: to match the input impedance of such a network to that of a specified source; to match the output impedance of such a network to that of a specified load; to make the input impedance of such a network substantially infinite; to make the input or output impedance of such a network substantially zero; to make the input and output impedances of such a network substantially alike in magnitude.

Related objects are to minimize or eliminate interstage coupling devices from translating apparatus of a plurality of stages, each of which comprises a semiconductor amplifier network, and to match the impedance of such apparatus as a whole to that of a specified source and its output impedance to that of a specied load.

Application Serial No. 11,165 of John Bardeen and W. H. Brattain, filed February 28, 1948, and now abandoned, describes and claims an amplifier unit of novel construction comprising a small block of semiconductor material, such as N-type germanium, with which are associated three electrodes. One of these. known as the base electrode, makes low resistance contact with a face of the block. It may be a plated metal film. The others, termed emitter and collector, respectively, preferably make rectier contact with the block. They may, in fact, be point contacts. The emitter is biased to conduct in the forward direction and the collector is biased to conduct in the reverse direction. Forward and "reverse are here used in the sense in which they are understood in the rectifier art. When a signal source isconnected between the emitter and the base and a load is connected in the collector circuit, it found that an amplied replica of the voltage of the signal source appears across the load. The aforementioned application contains detailed specifications for the fabrication of the device.

The device may take various forms, all of which have properties which are generally similar although they difer in important secondary respects. Examples of such other forms are described and claimed in an application of J. N. Shive, Serial No. 44,241, led August 14, 1948, and an application of W. E. Kock and R. L. Wallace, Jr., Serial No. 45,023, led August 19, 1948. The device in all of its forms has received the appellation transistor, and will be so designated in the present specication.

In the original Bardeen-Brattain application above referred to, there appears a tabulation of the performance characteristics of three sample translators. In one of these, it appears that increments of signal current which ow in the circuit of the collector electrode as a result of the signal current increments which ow in the circuit of the emitter electrode exceed the latter in magnitude. This feature of transistors has become the general rule, and appears in nearly all transistors fabricated. It is discussed in detail in an application of John Bardeen and W. H. Brattain, Serial No. 33,466, filed June 17, 1948, issued October 3, 1950, as Patent 2,524,035, which is a continuation in part of the earlier application of the same inventors. It is of such importance in connection with the present invention, as well as otherwise, that the ratio of these increments has been given a name, a In one of its aspects, although not exclusively, the present invention deals with transistors in which a 1 (a exceeds unity) and is based on the discovery that with a network of which such a device is the active element, the impedance looking into its input or output terminals can, by appropriate proportioning of one of the network parameters in relation to the transistor parameters, be made to take on values which vary over a much wider range than is possible with the most nearly analogous vacuum tube networks. It will be explained below, in the detailed description of the invention which follows, how it is that the value of a resistor included in the one circuit modifies the impedance of the other circuit.

The invention will be fully apprehended from the following detailed description of certain preferred embodiments thereof, taken in connection with the appended drawings, in which:

Fig. 1 is a schematic diagram of a transistor;

Fig. 2 is a symbolic representation of a transistor as employed in the present specification;

Fig. 3 is a schematic circuit diagram of a transistor amplifier network of the grounded base type;

Fig. 4 is the equivalent circuit of a transistor;

Fig. 5 is the equivalent circuit of the transistor network of Fig. 3;

Fig. 6 is a. group of graphs showing transistor parameter values as functions of emitter bias current;

' Figs. 7, 9 and 11 are graphs showing the varial ation of the input impedance of the netwcrkiot Fig. 13 with load resistance for three representative types of transistor characteristic; v l Figs. 16, 18 and 20 are graphs showing the variconditions;

Rig. 21 is a. schematic circuit diagram. oil a transistor ampliernetwork c! the grounded collector type;

Fig. 22 is the equivalentcircuit'ot 2.1;

Figs. 23. 25- and'2'7 are graphs showing the variation of the input impedance of. thev network. orv Fig. 21 with load resistance for three representav` tion types'of transistor characteristic;

Figs. 24, 26 andl 28 are graphs showing thefvariation of the output impedance or thenetwork ci Fig. 21 with source resistance under the sama conditions; A

Fig.. 29 ls a; schematic circuit'diagramshowing a modication of ther transistor amplier network of Fig. 2.1;

Fig'. 30 is the equivalent circuit diagramV of. the network ot- Flg. 29;. y.:

Figs. 31, 33 and 35 are schematic' diagrams showing further modifications of the transistor amplifier network of Fig. 2L;

Figs. 32, 34 and: 36 are the equivalentv circuits orthe networksoi Figs. 31, 33 and 35V respecd tively;

Fig. 37 is a schematic circuit diagram o! an amplifier comprising, a plurality of similar transistor amplifier stages in tandem;

Fig. 38 is a schematic diagram showing a-two stage ampliier of which theindividual stages are unlike;c

Figs. 39,. 40 and 41 are schematic circuit diagrams of modications of the amplifier of Fig. 38.

In Fig. 1 there is shown a diagraxrunaticfrepresentation of a transistor comprising a block l of semiconductor material, having a plated-film 2 of metal making low resistance contact with one face, an emitter electrode 3 and a collector electrode 4, making contact close together on the opposite face. A base electrode is connected to the film 2. To simplify the drawings, a symbolic representation, shown in Fig. 2, isl used henceforth.- In this gure, the emitter 3 is distin4 guished by an arrowhead which points inward for N-type material, the collector 4 by making contact on the same face of the block as the emitter, and the base electrode 5 by making contact on the opposite face. The short heavy line 6 repre sents the block itself,

Fig. 3 is a schematic circuit diagram ot a transistor amplifier network in which the transistor itself is represented by the symbol or Fig. 2.v A bias source l0 of perhaps 40 volts isconnected to apply negative bias potential to the collector 4, while another source. Il. usually of a fraction of a volt, is connected to apply a small positive bias upon ones point of view); A load represented by an impedance Z2, which may be variable, is connected in the collector circuit. A signal source l2 is connected in the inputcircuitd.- e., between the-emitter 3 and the basel l, mi addition, an

. external or source impedance Z1 is connected y ations of the output impedance of the network oi' 1 Fig. 13 with source resistance under the same A-in the input circuit. This impedance evidently 1 reduces'the signal voltage applied to the input terminals of the transistor, for given source voltage, but it serves an important purpose as will more fully appearfbelow.

Ag.- is nowI well known, the voltage which appears across the load impedance Zz contains a component which is an amplified replica o! the source' voltage; 1n addition, it is found 'that in the'gre'at. majority of transistors; a is so great that the signal frequency component of the collector current exceeds the signal frequency comlponent of the emitter current even when the net- Istant.;

York: loadl impedance Zn is of substantial'magniude.-

The' collector. signal currentccocrespondinzto iacgiven emitter signal current is, depends on the .a.= G)V-=const., grounded base conirectoir (1T er, e is equal to theratio off collector signet cur# rent-to' emltterslgnal ciment-whew the base' eicel trede-E is common tc the input and outputeir cuits-and when the collector voltage is held confn a network of thisv congumtion in'y which a constantpotential source* supplies' oper ating bias to the collector and in which signal frequencycollect'or currents' ow'iirough' a leid impedance Z and cause signal frequency changes inv the collector voltage', an equivalent dennitioi potential to the emitter 3 (or a small negative of c, namely.'

'I a 0(1) f m is more convenient touse.

Such an equivalent circuit is shown in Fig. 41. Theseelements of the equivalent circuit areidentitled herein as' emitter, collector and hase impedances, but it' is to' be understood' that an actual impedance ntasurement between two electrodes' of the transistor would notnecessarily lgive the simple sum of the respective two im# pedan'ces. The values of' the equivalent circuit Y elements may be arrived at. from such externa! impedance measurementsasfcilcws:

Ze=Z1lzl2 Zb=Z1a Z=Z22-'Zic- Zm=izx2 where e i. Zu isthe impedance measuredibetween thesmitter and thabase with theicollecton'circuit ci?" ectivelyfopen;

'I'he assumed directions of current flow and the polarity of the electromotive force of the internal generator I3 are as shownin Fig. 4 for the above measurements.

Fig. 5 is an equivalent circuit corresponding to the transistor amplifier network of Fig.3,which is of the "grounded base type; i. e., the base im.

pedance Zb is common to both meshes, while the emitter impedance Ze and the collector impedance Zc are individual to the first and second meshes, which are identified by mesh currents i1 and i2 in the customary manner. Test voltage sources e1 and ez are connected in the first and second meshes for purposes of analysis.

As with Fig. 4, there appears in series with the collector impedance a. source of electromotive force e'=Zmie (3) As above stated, the fictitious electromotive force e' which is characteristic of the transistor is found to be substantially proportional to the emitter current ie. The constant of proportionality thus has the dimensions of impedance, is termed a mutual impedance, and is designated Zm.

It is of interest to determine the relation which must hold in 'order that The foregoing definition (2) of a requires that it be determined when the output terminals of the transistor network are short-circuited for signal frequency currents. Furthermore. for the present purposes, the source can be treated as having no internal resistance. Thus, puttingr Z2=0 c2=0 (7) Z1=0 and solving the Equations 5 and 6 simultaneously for if and i2 gives Z, 7.2=e1iA- 6v except at very high frequencies and that, within this resistive. range, representative values are:

Thus both Zm andZ'c are many times as great as Zb; so that, from lo proximation,

Though the expressions developed hereinafter far input and output impedances are general, the results which follow will be illustrated with examples involving resistive terminations, and for that part of the frequency scale in which the transistor equivalent circuit parameters are resistive. These parameters; when used in this connection, will be referred to as re, rb, re and rm inf stead of Ze, Zb, Ze and Zm, respectively.

Out of the wide range of possible characteristics available among transistors, the results will be illustrated with three different sets of equiv-y alent circuit parameters. Therst, which will arbitrarily be referred to as type l, satisfies the following conditions ao a 1 and re=500 ohms rb=l00 ohms rc=20,000 ohms rm=10,000 ohms Type 2 characteristics are obtained when the following conditions are met:

Values of equivalent circuit parameters assumed to illustrate this type are:

re=500 ohms rb=l00 ohms rc=20,000 ohms rm=40,000 ohms Type 3 characteristics are obtained when a 1 o and y r.. f+n+r-T fs To illustrate this type, the following values are u assumed:

7`e=500 Ohms rb=600 ohms r=20,000 ohms m rm=40,000 ohms It is tobe understood that while all transis t' rs may be classified according to which of the three foregoing types they conform to, their values of the circuit parameters may vary wideLv from the particular combinations assumed above.

Equation 10, to a good ap- Indeed, the parameters for any one transistor vary with operating conditions, as is illustrated on Fig. 6, `which shows typical characteristics of re, rs, re and rm plotted against emitter bias current; l. e., steady current flowing to the `emitter electrode (Ie). At the operating point of 0.5 mllliampere emitter current, it will be eeen that r===500 ohms n: 1'00 ohms ,Y r=20,000 ohms rm=40,000 ohms By .an exactly similar process, putting but allowing Z1 and e2 to remain nite, it turns assuming Z1 and Z2 to be replaced by R1 and Rz.

In transistors of type 1, a 1, so that rm r, and both of these expressions give positive values for all positive values of R1 and Rz. The variation of Rm'and Rott with R2 and R1, respectively, is small. The variations of R111 and Reut are plotted in Figs. 7 and 8 as functions of R2 and R1, respectively, for the type 1 transistor whose parameters were given above. The input resistance, as shown in Fig. 7, varies between 550 and 600 ohms for a variation of-Ra between zeroV and innity and the output resistance, as shown in Fig. 8, varies between 18,400 and 20,100 ohms for a variation of R1 between zero and liliinity.I

In transistors of type 2, a 1 but Tm r.l'n+r;" (16) The variations of Rin and 'Rim with R1 and Rz as shown on Figs. 9 and 10 for a transistor of this type'are somewhat greater, but both are still positive for all positive values of R1v and Re.

8 WithI the type 3 transistor parameters, where w 1 and rm n+niff9 (i7) startling new results are obtained. 'I'fh'ese are revealed in Figs. 1l and 12, which are plots ofA input resistance as a function of Rz and of output resistance as a function of R1. It is apparent -that both the input resistance and the output vresistance pass through zero values, for critical values of 4R2 and R1, respectively, and are positive for greater values and negative for smaller. Thus there is furnlshed'a transistor network capable of giving amplification, and which has zero or negative input resistance 'or zero or negative output resistance. Furthermore, these results are independent of one another. so that 'they may be 'obtained separately ortogethenas desired, Within the limitations imposed byst'ability' requirements. It will be evident from inspection of Figs. 11 and 12, that this arrange'- m'ent is not fshort-circuit stable.l That is, if both R1 and'Rz are zero, the network may break into oscillation because of the negative resistances of the input and output circuits, Ii"

R1=0, VR2 must be at least 1550 ohms, o'r' if R1=`0, R1 must be at least 8215 ohms to obtain a stable arrangement. The critical value of Rz, for which R1n='0`, is given by simiiari'y, the output resistance Reut-1s zero fr ram-:wg R1 Tci'rb re Transistor networks of the type shown in Fig'. 3, in which the'i'nput or output resistance has been adjusted in the manner described above tb have a zero value, are of use in current measuring instruments. Those in which the resistance has been adjusted to a negative value are of use as negative resistance boosters, and the like; 0n the other hand, 'and especially when 1, the invention provides a simple and convenient adjustment of the magnitudes of the input and output lmpedances of such networks to match positive -soilrce and load impedances. respectively.

Fig'. 13; shows a transistorconnect'ed into anet-i work of the so-called grounded emitter" type. its shown by the equivalent circuit, Fig. 14, thl's term means merely that the emitter impedance Ze is common to the two meshes whileI the base impedance Zb and the collector impedance Ze are individual to the separate meshes. The fictitious electromotive force e which is character'- istic of the transistor is again given by but the emitter current is is now replaced by the difference between the mesh currents i1 and in. Thus As before, a test voltage source e1 and an input impedance Z1 are connected to the input terminals while a second test voltage source en and a load impedance'Zs are connected to' the output terminals. Mesh equation analysis of the circuit of Fig. 14 in' the manner outlined above gives These may also be rewritten for frequency ranges which are-.not too high, as

andv

'Zonen-ZV1' (21) where Z1 and Z2 are replaced by R1 and R1. These latter expressions are plotted as functions of R2 and R1, respectively;

(a) 'In Figs. 15 and 16 for the illustrative paramleter values previously chosen for type 1 transistors, with which a 1 and (b) .In Figs. 17 and 18 for the illustrative parameter values previousy chosen for type 2 transistors with which a 1 and Zie Tb (c) In Figs. 19 and 20 for the illustrative parameter values previously chosen for type 3 transistors with Iwhich a 1 and With the type 1 transistor characteristic in which a 1, the input and output resistances remain positive for all values of R2 and R1, respectively, though their magnitudes are controllable by adjustment of these resistors.

But when a 1, startling results occur. Thus, in Figs. 17 and 19, the input resistance becomes infinite for a load resistance given by R2=m1'e*7'c (22) being positive for greater values and negative for lesser values. In addition, and subject to the condition 1* 1 n. r. -lra The value of R1 becomes zero when 're'rc 1`m 1'e" 7;c 'rb being positive -for lesser values and negative for greater.- For a type 3 transistor, for which the output impedance is always negative, but is variable over a wide range of adjustment of R1.

The network of Fig. 13, when adjusted in the manner described above, in addition to providing ,.amplication, is useful for matching impedances.

as a negative resistance, as a zero impedance device, and in various other connections.

Fig. 21 shows a transistor connected in a network of the so-called grounded collector type. As shown by the equivalent circuit, Fig. 22, this term means merely that the collector impedance Ze is common to the two meshes while the base impedance Zh and the emitter impedance Ze are individual to the separate meshes. The ctitious f electromotive force e' which characterizes the transistor performance is again connected .in series with Ze and is given by but in4 this case Test voltage sources e1 and e2 and source and load impedances Z1 and Zz are connected between the input terminals and between the output terminals, as before. Mesh equation analysis of the ciircuit of Fig. 20 in the manner outlined above g ves and Considering the less general case of purely re sistive elements. We have on rewriting:

and

when R1 and R2 are substituted for Z1 and Z2, re-

spectively. These resistances are plotted, as functions of R2 and R1, respectively,

(a) In Figs. 23 and 24 for a transistor of type 1,

in which (b) In Figs. 25 and 26 for a transistor of type 2,

in which [a 1 t mkh-trulli? (c) In Figs. 27 and 28 for a transistor of type 3,

in which It will be noted that the curves of these figures are the same in many particulars as those of Figs. 15 to 20. Thus, the conditions under which Rin reaches ininity in Figs. 25 and 27 are identical with those for which the same result arises in Figs. 17 and 19. Again, the conditions for which Roue reaches zero in Fig. 26 are the same as those for which the like result occurs in Fig.

. Rout=0,

accises 1 18.1 'rho 'particular values of ai and ai which give these results are f which isfidentioai with the voirie of Ri :or which Rooi reaches zero inv Fig. 18. 'Ihe value of Ra transistors of type 3, is

-The network of Fig. 21, when'adiusted in the? manner described above, can be put to use in any of the various connections above referred to in connection with the other figures.`

It wiii be observed that in eigen-oranti 2v,"

resistance for any and all values of source re'' sistance between zero'.-a,nd iniinity: This negative "resistance" is of the sosc'alled series-type,

i. e., the network of which it forms a part will be stable only ii a positive resistance is connected in sei-ieswith( it, iot`=which the. value is greatr than that'o'! the negativ-e'iesistance. By way of example, assume that the source Vresistahoe'n'ff is" zero: fri-om vFiizrzu; the output impedance then appar's as' negative `resistance of -1550 ohms. Ii a load resistance R2 equal to orcgreater thanfldhinsls connected to the output terminals of-'theitrahsistor network, the network as a whole will be stable. the value of the external load resistance is less than 1550 ohms,`th'e` riet'resistance inthe output circuit will be negative and the network will oscillate or sing. Addition of .resistance Ri in theinput circuit doesnot ciir'e"thev situation but only makes things worse, because, as shown by Fig. 20 any increase of'source resistance `above zero "causes a larger negative' value of the output impedance of the network, which therefore requires a correspondingly largervalue of load resistance to prevent oscil1 ation,\

Thus, if the external load resistance has a positive value, which is less in magnitude than the' negativefoutput resistance forfzero input re'- sistance, the system as a whole will beinherently unstable, even though its input impedance appears to be positive. as indicatediin those parts of Fig. 19 which lie irrithe shaded area.

The explanation of instability in the case of Fig.27 is the same as that ot Fig. 19 except for numerical values.

With the networks described above, it is possible to design a single amplifier stage whose input impedance or output impedance is respectively matched to the impedance of a source or o., .a load as long as these are not too high or toa low.- A,further.problem arises when one oi'othemis infinite. or'zero. Take, for' example, theion'im0n-s situation in..which it isdesired that the .input impedancefof an al'nplier be. substan-vv tially innitewhile itsoutput impedance has a If, however,

i for which Rin has a zero value, in the case of..

specified value betweenzero and infinity. This probie may 'be'illstr'ate'd in'4v connection with Fig. 21. "The input' impedance may be madev inilnite, by so choosing Ra* that the denc'iminatorltY or (25)/ vanishes; but it ,may happen that the load with which the network is'to work has a resistance of widely different value. i

' This problem is solved, in accordance with the' invention in one of its aspects, by the use oi an' additional variable,parameter in the form of a padding resistor. v

it may hereodui aopreoiaied'that the addition of a resistance in series with emitter, base, or'l collector is equivalent in eiect izo-increasing the -magnitude of ro, rb'or ro respectively, in the fore? going equations for input and output resistance. Fig; 29 illustrates 'the principle as appliedto the grounded collector network or Fig..21, and Fig.'

30 shows the equivalent circuit. It differs from Fig. 22 bythe addition of the padding resistor Rp in series with the collector. So-

lution of the network equations in the manner heretofore described but for resistances directly, instead of for the more. general impedances yields, for the input resistance:

(rc-FRIO (re'i'R-Z) It.is-evident fromy these equations that the4 padding resistor and is therefore not available to the load. Under some circumstances this maybeV objectionable; and to reduce this power loss'Y without sacricing the impedance matching -a d vantages of Fig. 29, resort may be had tomstill' another transistor network which is illustrated' in Fig. 31, while its equivalent circuit is shown in Fig. 32. 'Ihis network is the same as that of Fig.'

.mesh to the network, designated is in Fig.' 32.

equations yields, for the in- 'I Rin v,and for the output resistance:

RiRp

From Equation ai it is evident that, within the restriction rm (Rz-i-n-i-re) the input impedance may take'on values which are positive, negative, zero, 'or inilnite. asre- (cio) i quired, in dependence on the values of R2 and Rr.

This evidently gives' greater freedom in the selection of the load resistance. as compared with Equation 25 which applies to the network oi Fig.'-

21, in the same manner that the use o f the pad-.- ding resistor in Fig. 31 provides such freedom. At the same time, all of the power output of the transistor is furnished to the load. at the exasuma.

powerisdri-ven 1from thersouroe. rather thanfrom transistor. .':This difference is of advantage 'underaomecircumstances.

`Inrthe vacuum tubeamplifier art, it=iszknown thatcertatn i-a'dvantages` accruefrom the use of negative-,or inverse feedback. 'The conventional cathode follower vacuum tube circuit with large,

unbypassed cathode resistor embodies the :in-

versefeedback principle, and, as is well known; the input impedance of such a circuit, lookinginto its grid'and load resistor terminals is greatly increased, as compared with that of a grounded cathode circuit employing the same tube. The networks of Figs. 21, 29 and 31 may 1 bcflooked upon as embodying thesame negative feedback principle but they diier from. the most nearly analogous vacuum tube circuits in that the :input impedance may take on .the widely varying .values discussed above. The effect of the resistor Rr in Fig.'31 may be looked uponas fur" ther-:increasing the inverse `feedback of Fig. 21 byfproviding a second path, in addition to that through thesource resistance R1, through which the-feedback current can flow, and so furnishing a-'greatercurrent tothe base electrode for a given voltage 'drop across the load resistor, or a greater voltage `feedback for a given emitter current, depending on one-s point of view. The mode of operation of the network of Fig. 31 can also be lookedmpon as follows: Elimination ofthe padding resistor Rp. of Fig. '29 `effectively reduces'the total resistance in the output circuit of the transistor below the value at which thei-nput im.- pedance becomes infinite. As a result, the input impedance of the transistor, without the feedback resistor-RF, is negative. InsertionV of the feedback resistor RF of the proper magnitude now places a positive resist-ance. in shunt with the negative input resistance of the transistor network of justsuch a magnitude as to bring the input impedance of the network as a whole back to infinity.

'.Still further flexibility results when the padding resistorRp of Fig. 29 and the 'feedback re sister Rrof Fig. 31 are embodied in the saine transistor network. Such a network is shown in Fig. 33 and its equivale-nt circuit is shown in Fig. 34; The expressions for the input and output impedances are like those for Fig. 31 but for the fact .that the collector resistance rc is to be replaced, wherever it occurs, by

Ted-'Rn and jthatthecondition (32) is replaced by Tm` (R2 -I-Te-l-Tc-I-Rp) (33) Instead of merely increasing the inverse feedback due to Rz bythe use of a shunting resistor as in Fig. 33, an additional negative feedback current may be drawn from the collector and fed to the base electrode by way of a feedback resistor Rr, as in Fig. 35. Here C1 and Cz'are merely-,blocking -condensers of negligible impedance atsignal frequencies and are omitted from the equivalent circuit Fig, 36. The resistor R'r'therefore carries --a currentto the base electrode, which current is in phase with the collector lvoltage. In theabsence of the feedback path, there is a phase reversal between `the voltage on the .base elec.- trode andthe voltage on the collector. Therefore thefeed-back furnished by way of the resistor'R'r` isnegative -or degenerative, and its use carries with it allor fthe advantages which are now 4Well f; comesinfinitesubiect to the same condition (33) and for slightly different values of Re, Rr and-Rp. The differences, though slight from lthe analytical standpoint, may become critical in particu1ar. cir cumstances. f

The various networks of the invention may be coupled together in various ways. Fig.'j37' shows a-threestage amplifier coupling an injcoming line 20 to an outgoing-line 2|. characteristic impedance -ofthese lines may be alike." The operation of tandem stages without using inter-stage transformers presents a problem tol the designer of transistor-networks who has-not the benefit of thepresent invention. The input -re sistance of the first stage may be matched to the resistance of -the source, that is ofthe incoming line 20, by use of the appropriate transformation ratio in an input transformer 22. In each stage the resistances R3' and R4 may be assumed'to'be rb ohms Vre =500 ohms To =20,000 ohms rm =40,000 ohms The output load on the first stageis the -sum of Rs and the input impedance of the -following stage. Equation 20a is a general expression for the input resistance of a grounded emitter transistor amplier stage as a -function of its load resistance. In this expression, replacing R2 by Rs-l-Rin gives Insertion of the numerical values listed above in this expression gives Equation 21a is likewise a general expression for the output impedance of a grounded emitter stage as a function of its input terminating resistance R1. Introducing the condition that the impedance of each stage shall be matched, at its input terminals, to its input termination, i. -e,,- Ri=R1n, gives Rin=100+ Inserting the foregoing numerical values, with ARin still undeterminedngives The conditions of the problem are that the input terminating resistance of each stage shall be animan L.

output .impedance 1 'of1 the 'prior' stage, or

.V aia-#asignan i gives,.for the assumed numerical values:y

Rinh ohms y Rut=-15,600 ohms Rs=2.0.1 ii Ohms Since` the stages are all tobe alike, this -result holds for any stageso that a multistage,amplifiery of as many stages as may be desired can be built up, in which all input and output impedances are 4,590ohms, and in which, furthermore ,lthe ef-I fective output `impedance of the last stage (Root-Hts) is likewise 4,500 ohms. Transformers` 22, ,28, or other impedance matching networks may now be connected at the inputand output terminals of the amplifier as a whole to effect a match to the incoming and outgoing lines 20, 2 I. Each stage'of the amplifier, using the assumed numerical values, has a power gain of 18 decibels, which would be impossible to secure in a multistage amplifier in which interstage impedance matching was. obtained, merely by the use of, padding resistors in series with the input circuits and potentiometers in the output circuits.

It will be noted that, in Fig. 37, the emitter bias battery Il of ,the earlier figures has been omitted. It is replaced, in the first stage,y by a self-biascircuit of the typewhich forms vthe subject-matter of an application of R. C. Mathes and H. L. Barney. Serial No. 22,854, filed April 23. 1948, and issued August 8, 1950, as Patent 2,517,960, and in the second and third stages byV a diii'erent self-bias arrangement, which forms the subject-matter of an application of H. L.

' Barney, Serial No. 123,507, filed October 25, 1949.

stage.' Thus condition (al may be met by se# lecting the first stage output termination in 'ac'- ccrdance with Equation a.; condition (b) is metvby selecting the second stage output terminatio'nfin accordance with Equation 25a at such a value that its input impedance is equal tothe output impedance of the first stage as just determined, and, lastly, condition (c) is met by constructing the resulting output termination'.

ofI two parts, the load itself and -an adjustmentresistor R's. The latter ,is shown in shunt with" the load.v Circumstances may require that itfb'e 3)', while the second stage is of the emitter-foil;-4 lower typewith padding resistor Rp (Fig. 29).1'

Transistors vhaving type 1, 2 or 3 characteristics' may be used in either stage of this' amplifier? and ground. The resistor Rv is by-passed for signal frequency purposes by the condenser C'z but it carries a potential drop which is nearly equal in magnitude to that across the shunt resistor R4. By this means self-bias of the base electrodewith respect to the emitter in the required magnitude of a fraction of a volt isser` cured for the transistors of the second and third stagesY without resort to an interstage transformer." 4

Under some circumstances the restrictions placed on the amplifier of Fig. 37 may be considered 'too severe. For most purposes a SufB- cient requirement is that (a) the input imped-r anceof the first stage of an amplifier match the source impedance; (b) the output impedance ofeach stage match/ the input impedance ofthe following stage; and (c) the output impedance of the last stage match the impedance of the load. Requirements of this type may be met comparatively simply in a two-stage amplifier The resistors Rs, Re and Rs, of which R5 and Rs are self-bias resistors, merely serve to apply correct operating potentials to the electrodes. With the compensating 'resistors Rv and R'v in the cir-A cuit, Rs and Ra may be of such large value asv by the rst stage is the input impedance of the' second. In the manner explained above, but using the impedance expressions appropriate to the networks, namely, Equations 14 and 15 for the' first stage and 29 and 30 for the second, and finally selecting the adjustment resistor R'1 so that when it is connected in parallel with the load as show n, or in series with the load, this combination of resistor Rv and the load pre-y sents the necessary impedance to the output ter-- minals of the second stage.

In place of "the padding resistor Rp of Fig. 39, the 'feedback resistor RF of Figs. 33 and 35 may be employed, if desired, to give flexibility to theI choices of the other resistors. Fig. 40 shows a two-stage amplifier in which the second stage is vlike Fig. 31, and Fig-41 shows one in which the second stage islike that of v Fig. 35. The impedance matching principles, and the manner in which they are to be put in practice, are as explained above, due regard being -had to the exf- ,pressions governing the input and output imence is made to another divisional application, Serial No. 127,439, filed November 15, 1949, and

to a related original application Serial No. 58,685, filed November 6, 1948. What is claimed is: 1. An amplifier having an adjustable input impedance and an adjustable output impedance which comprises a transistor comprising a semiconductive body, a -base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of short-circuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an output circuit interconnecting said emitter and said collector, an input circuit interconnecting one of said last-named electrodes with said base electrode, an impedance element connected in series with said collector, and a i anima l -feedback path including another impedance element, coupling said collector to said base electrode.

2. An amplifier having an adjustable input impedance and an adjustable output impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of short-circuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an output circuit interconnecting said emitter and said collector,- an input circuit interconnecting one of said last-named electrodes with said base electrode, a terminating impedance element in said input circuit, a load in said output circuit, and an impedance element connected in series with said collector.

3. An amplifier having an adjustable input impedance and an adjustable output impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of short-circuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an output circuit interconnecting said emitter with said collector, an input circuit interconnectng one of said last-named electrodes with said base, and a feedback path including an impedance element coupling said collector to said 'base electrode.

4. An amplifier network having an adjustable input impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of shortcircuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input 'circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode and said collector electrode, and a load resistor R2 connected in said output circuit, said resistor being proportioned in accordance with the formula Tc(7`a+R2) R where re=emitter resistance of the transistor rb=base resistance of the transistor Irc=collector resistance of the transistor rm=mutual resistance of the transistor Rin=input resistance of the transistor network to cause the input impedance of the network to have a desired value.

1 A5. An amplier network having an adjustable output impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of shortcircuit collector current increments to emitter current increments which, under proper conditions of electrode .bias is greater than unity.

means including` an energy source for establishing said proper bias conditions. an input circuit interconnecting said base electrode and said collector'electrode, an output circuit interconnecting said emitter electrode' and said collector electrode, and a terminating resistor R1 connected in said input circuit, said resistor being proportioned in accordance with the formula (RVi-rb) (ru-rm) Rouw-Tri-W where ria-:emitter resistance of the transistor rb=base resistance of the transistor ref-:collector resistance of the transistor rm=mutual resistance of the transistor Roun=output resistance of the transistor network to cause the output impedance of the network to have a desired value.

' 6. An amplifier network having an adjustable input impedance which comprises a transistor comprising a semiconductive-body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of shortcircuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode and said collector electrode, a load resistor R2 connected in said cuput circuit and a resistor Rp connected in series with said collector electrode, said resistors being proportioned in accordance `with the formula 4rc=emitter resistance of the transistor rb=base resistance of the transistor r=col1ector resistance of the transistor rm=mutual resistance of the transistor Rin=input resistance of the transistor network to cause the input impedance of the network to have a desired value.

7. An amplifier network having an adjustable output impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of shortcircuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode and said collector electrode, a terminating resistor R1 connected in said input circuit and a resistor Rp connected in series with said collector electrode. said resistors being proportioned in accordance with the formula Trl-N+ RVi-R1, where re=emitter resistance of the transistor rb=base resistance of the transistor rc=collector resistance of the transistor rm=mutual resistance of the transistor Reuz--output resistance of the transistor network anims to cause the output impedance of the network to have a desired value.

8. An ampliiier network having an adjustable input impedance which comprises a transistor comprising asemiconductor body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor l'being characterized by a ratio of short-circuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode and said collector electrode, a load resistor Rz connected in said output circuit and a negative feedback path including a resistor Rr coupling said collector to said base, said resistors being proportioned in accordance with the formula where n=emitter resistance of the transistor =base resistance of the transistor r=collector resistance of the transistor 1m=mutual resistance of the transistor Rm=input resistance of the transistor network to cause the input impedance of the network to have a desired value.

9. An amplifier network having an adjustable input impedance and an adjustable output impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith,- said transistor being characterized by a ratio of short-circuit collector current increments to emitter current increments which, under proper conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode and said collector electrode, a terminating resistor R11 connected in said input circuit, a load resistor Rz connected in said output circuit, and a resistor Rp connected in series with said collecto said resistors being proportioned in accordance with the formulae Triand

r=emitter resistance of the transistor rb=base resistance of the transistor rc=collector resistance of the transistor rm=mutual resistance of the transistor Rm=input resistance of the transistor'network Rou=output resistance of the transistor network to cause the input and output impedances of the network to have desired values.

10. An amplier network having an adjustable output impedance which comprises a transistor comprising a semiconductive body, a base electrode. an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of shortcircuit collector current increments to emitter 20' current increments which. under proper condi tions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode and said collector electrode, a terminating resistor R1 connected in said input circuit, and a negative feedback path including a resistor Rr coupling said collector to said base, said resistors being proportioned in accordance with the formula RIRr Rl+ RF'i-rb) (T0-rl) where to cause the output impedance of the network to have a desired value.

' 11. An amplifier having a substantially zero input impedance which comprises a transistor comprising a, semiconductive body, a base electrode. an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of short-circuit collector current increments to emitter current increments which, under proper conditions oi' electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an input circuit interconnecting said base electrode and said collector electrode, an output circuit interconnecting said emitter electrode with said collector electrode. and a load resistor R.: connected in said output circuit, said resistor having a value given substantially by the formula Where r=emitter resistance of the transistor rb=base resistance of the transistor r=coi1ector resistance of the transistor rm=mutua1 resistance of the transistor.

12. An amplifier having a substantially zero output impedance which comprises a transistor comprising a semiconductive body, a base electrode, an emitter electrode and a collector electrode cooperatively associated therewith, said transistor being characterized by a ratio of shortcircuit collector current to emitter current which, under conditions of electrode bias is greater than unity, means including an energy source for establishing said proper bias conditions, an output circuit interconnecting said emitter electrode with said collector electrode, an input circuit in terconnecting one of said last-named electrodes with said base electrode, and a terminating resistor R1 connected in said input circuit, said resistor having a value substantially by the formula r=emitter resistance of the transistor rb=base resistance of the transistor r=collector resistance of the transistor rimmutual resistance of the transistor.

' 21 13. An ampliner having a substantially inflnite input impedance which comprises a transistor comprising a. semiconductive body. a base electrode, an emitter electrode and a collector elec-'- trode cooperatively associated therewith. said'A with said base electrode, and a load resistor It:

connected in said output circuit, said resistor having a value given substantially by the formula R2=fmrerc where r=emitter resistance of the transistor =base resistance of the transistor r=co1lector resistance of the transistor l0 rm=mutual resistance of the transistor.

HAROLD L. BARNEY.

No references cited. 

